# Two-port network

A **two-port network** is an electrical circuit with two *pairs* of terminals. As shown in the figure, two terminals constitute a **port** *only* if they satisfy the essential requirement known as the **port condition**, namely, the same current must enter and leave a port.^{[1]}^{[2]}
Examples include small-signal models for transistors (such as the hybrid-pi model), filters and matching networks. The analysis of passive two-port networks is an outgrowth of reciprocity theorems first derived by Lorentz.^{[3]}

A two-port network makes possible the replacement of either a complete circuit or part of it by a "black box" with only four distinct parameters, enabling us to separate its behavior from that of its internal constituents, thus simplifying analysis. Any linear circuit with four terminals can be transformed into a two-port network provided that it does not contain an independent source and satisfies the port conditions.

The parameters used to describe a two-port network are the following: z, y, h, g. Each choice corresponds to a different choice for which pair of variables from port 1 and port 2 are chosen to be independent, externally applied sources and which two will be the dependent resultant variables determine by the two-port parameters (see the figure). The port currents and voltages are denoted as follows:

*V*= Port 1 voltage_{1}*I*= Port 1 current_{1}*V*= Port 2 voltage_{2}*I*= Port 2 current_{2}

The relations between inputs and outputs usually are expressed in matrix notation.

These variables are most useful at low to moderate frequencies. At high frequencies (for example, microwave frequencies) power and energy are more useful variables, and the two-port approach based on current and voltages that is discussed here is replaced by an approach based upon scattering parameters.^{[4]}

Though some authors use the terms *two-port network* and *four-terminal network* interchangeably, the latter represents a more general concept. **Not all four-terminal networks are two-port networks.** A pair of terminals can be called a *port* only if the current entering one is equal to the current leaving the other (the **port condition**). Only those four-terminal networks in which the four terminals can be paired into two ports can be called two-ports.^{[1]}^{[2]}

## Impedance parameters (z-parameters)

The figure shows the two-port driven by two external current sources, making the input currents *I _{1}* and

*I*the independent variables controlled from outside the two-port. By convention, dependent sources (controlled by the independent sources) are depicted using diamond shapes. The port voltages are determined in terms of these input currents by the

_{2}*z*-parameters defined by:

- .

Notice that all the series connected elements represented by z-parameters have dimensions of ohms, as do the dependent source parameters.

### Example: bipolar current mirror with emitter degeneration

The figure at left shows a bipolar current mirror with emitter resistors to increase its output resistance.^{[5]} Transistor *Q _{1}* is

*diode connected*, which is to say its collector-base voltage is zero. The figure at right shows the small-signal circuit equivalent to the transistor circuit. Transistor

*Q*is represented by its emitter resistance

_{1}*r*≈

_{E}*V*(

_{T}/ I_{E}*V*= thermal voltage,

_{T}*I*= Q-point emitter current), a simplification made possible because the dependent current source in the hybrid-pi model for

_{E}*Q*draws the same current as a resistor 1 /

_{1}*g*connected across

_{m}*r*. The second transistor

_{π}*Q*is represented by its hybrid-pi model. Table 1 below shows the z-parameter expressions that make the z-equivalent two-port electrically equivalent to the small-signal circuit for the mirror.

_{2}Table 1 | Expression | Approximation |
---|---|---|

In this table, the bipolar transistor *emitter resistance* denoted *r _{E}* is defined as:

and the notation '||' indicates the resistance of resistors in parallel:

The negative feedback introduced by resistors *R _{E}* can be seen in these parameters. For example, when used as an active load in a differential amplifier,

*I*, making the output impedance of the mirror approximately

_{1}≈ -I_{2}*R*≈ 2 β

_{22}-R_{21}*r*/(

_{O}R_{E}*r*) compared to only

_{π}+2R_{E}*r*without feedback (that is with

_{O}*R*= 0 Ω) . At the same time, the impedance on the reference side of the mirror is approximately

_{E}*R*≈ , only a moderate value, but still larger than

_{11}-R_{12}*r*with no feedback. In the differential amplifier application, a large output resistance increases the difference-mode gain, a good thing, and a small mirror input resistance is desirable to avoid Miller effect.

_{E}## Admittance parameters (y-parameters)

The figure shows the two-port driven by two external voltage sources, making the input voltages *V _{1}* and

*V*the independent variables controlled from outside the two-port. The port currents are determined in terms of these input voltages by the

_{2}*y*-parameters defined by:

- .

where

The network is said to be reciprocal if . Notice that all the shunt-connected elements are represented by y-parameters with dimensions of siemens, as are the dependent source parameters.

## Hybrid parameters (h-parameters)

The figure shows the two-port driven by two external sources, a current source at port 1 and a voltage source at port 2, making the input current *I _{1}* and input voltage

*V*the independent variables controlled from outside the two-port. The voltage at port 1,

_{2}*V*, and the current at port 2,

_{1}*I*, are determined in terms of these inputs by the

_{2}*h*-parameters defined by:

- .

where

Often this circuit is selected when a current amplifier is described, because the port 1 input is the independent input current and port 2 output is the dependent current.

Notice that off-diagonal h-parameters are dimensionless, while the series-connected diagonal element has dimensions of ohms, while the shunt-connected diagonal element has dimensions of siemens.

### Example: common-base amplifier

The bipolar common-base amplifier is shown at left. The current source in the collector lead is an ideal DC source, and as such will not allow passage of any varying signal through itself. Its purpose in the circuit is to provide a DC bias current that sets the operating point (the quiescent transistor state about which the transistor varies in processing the signal; see the article Mode (electronics).). A signal *current* is applied to the emitter, and an output *voltage* is required at the collector. The output node is shown as an open circuit (no load) at the left, but to make use of the amplifier, a load can be attached, which then will draw a signal current from the collector node.

The small-signal circuit at the right assumes the voltage at the collector is a specified variable, and the output current is to be determined. The input current at the emitter also is a specified variable, and the signal voltage *V _{E}* developed at the emitter is a dependent variable.

Tabulated formulas in Table 2 make the h-equivalent circuit of the transistor agree with the small-signal low-frequency circuit found using the transistor hybrid-pi model at the right. Notation: *r _{π}* = base resistance of transistor,

*r*= output resistance, and

_{O}*g*= transconductance. The negative sign for

_{m}*h*reflects the convention that

_{21}*I*,

_{1}*I*are positive when directed

_{2}*into*the two-port. Parameter

*h*represents the

_{21}*current gain*of the circuit viewed as a current amplifier. A non-zero value for

*h*means the output voltage affects the input voltage, that is, this amplifier is

_{12}**bilateral**. If

*h*= 0, the amplifier is

_{12}**unilateral**.

Table 2 | Expression | Approximation |
---|---|---|

<< 1 |

The transistor β is related to the transistor transconductance *g _{m}* as:

## Inverse hybrid parameters (g-parameters)

The figure shows the two-port driven by two external sources, a voltage source at port 1 and a current source at port 2, making the input voltage *V _{1}* and input current

*I*the independent variables controlled from outside the two-port. The current at port 1,

_{2}*I*, and the voltage at port 2,

_{1}*V*, are determined in terms of these inputs by the

_{2}*g*-parameters defined by:

- .

where

Often this circuit is selected to describe a voltage amplifier, as the port 1 input is an independent voltage, and the port 2 output is a dependent voltage. Notice that off-diagonal g-parameters are dimensionless, while the series-connected diagonal element has dimensions of ohms, while the shunt-connected diagonal element has dimensions of siemens.

### Example: common-base amplifier

The common-base amplifier is shown again at the left. This time, a signal *voltage* is applied to the emitter, and an output *current* is taken from the collector.

The small-signal circuit at the right assumes the current at the collector is a specified variable, and the output voltage is to be determined. The input voltage at the emitter also is a specified variable, and the signal current driven into the emitter is a dependent variable.

The tabulated formulas in Table 3 make the g-equivalent two-port for the amplifier agree with the small-signal circuit found using the small-signal low-frequency hybrid-pi model for the transistor. Notation: *r _{π}* = base resistance of transistor,

*r*= output resistance, and

_{O}*g*= transconductance. Parameter

_{m}*g*represents the voltage gain of this circuit viewed as a voltage amplifier. The negative sign for

_{21}*g*reflects the convention that

_{12}*I*,

_{1}*I*are positive when directed

_{2}*into*the two-port. A non-zero value for

*g*means the output current affects the input current, that is, this amplifier is

_{12}**bilateral**. If

*g*= 0, the amplifier is

_{12}**unilateral**.

Table 3 | Expression |
---|---|

## References

- ↑
^{1.0}^{1.1}P.R. Gray, P.J. Hurst, S.H. Lewis, and R.G. Meyer (2009). “§3.3: Basic single-transistor amplifier stages”,*Analysis and Design of Analog Integrated Circuits*, Fifth Edition. New York: Wiley, pp. 173*ff*. ISBN 978-0-470-24599-6. - ↑
^{2.0}^{2.1}R. C. Jaeger and T. N. Blalock (2006).*Microelectronic Circuit Design*, Third Edition. Boston: McGraw-Hill, §10.5 §13.5 §13.8. ISBN 9780073191638. - ↑
See review by Jasper J. Goedbloed (2003). Reciprocity and EMC measurements.
*Presentation at 2003 EMC Zurich Symposium*and as*IEEE EMC EMCS Newsletter*pp.93-104. - ↑ David M. Pozar (2005). “Chapter 4: Microwave network analysis”,
*Microwave Engineering*, 3rd Edition. John Wiley & Sons, pp. 161-221. ISBN 047164451X (Softcover). - ↑
The emitter-leg resistors counteract any current increase by decreasing the transistor
*V*. That is, the resistors_{BE}*R*cause negative feedback that opposes change in current. In particular, any change in output voltage results in less change in current than without this feedback, which means the output resistance of the mirror has increased._{E}